ISL70617SEH Datasheet, PDF (23/28 Pages) Intersil Corporation – High voltage process control

ISL70617SEH
TABLE 3. 1kHz INPUT NOISE AND THERMAL NOISE CONTRIBUTIONS
R_IN R_FB
A_V (kΩ) (kΩ)
1 30.1 30.1
A_V x e_N(I)
(nV/√Hz)
8.6
2 x A_V x i_N(I)
x 500Ω
(nV/√Hz)
0.15
A_V x √(4kT x R_IN) √(4kT x R_FB)
(nV/√Hz)
(nV/√Hz)
22.3
22.3
R_FB x i_N(I_ERR)
(nV/√Hz)
78
e_N(FB)
(nV/√Hz)
8.6
1 121 121
8.6
0.15
44.6
44.6
300
8.6
100 0.301 301
860
15
223
22.3
78
8.6
100 1.21 121
860
15
446
44.6
300
8.6
NOTE:
17. e_N and i_N values are chosen for illustration purposes and may not reflect actual device performance.
e_N (RTO)
OUTPUT
REFERRED
NOISE
(nV/√Hz)
e_N (RTI)
INPUT
REFERRED
NOISE
(nV/√Hz)
86
307
896
8.9
1015
10.15
Driving an ADC
The output feedback loop is closed by the connection of +V_OUT to
the +V_FB pin and -V_OUT to the -V_FB. The V_CMO pin is just an input to
a very low bias current terminal, and would be connected to a
mid-scale voltage when driving a single supply ADC, such that the
input would have a ± input signal span. Where V_CMO is connected
to the ADC ground, only positive inputs would be converted by the
ADC.
Input and Feedback Amplifiers
The input and the output linear dynamic ranges are set by class-A
biasing on the R_IN resistor for the input stage, and the R_FB
resistor for the output stage (Figure 48). Unity gain buffers force
the differential voltages across each resistor to the maximum of
100µA*R produced by the current sources. While the voltages
impressed across these resistors will continue to move with
overloads beyond this value, they will not be linear. A good rule of
thumb is to keep the maximum linear dynamic range to less than
~80% of the maximum I*R voltage across the resistors
(Equation 8).
At equilibrium, the amplifier forces the resistor currents to be the
same so that their voltages match the desired gain ratio,
R_FB/R_IN; however, during transient conditions, the currents
remain unequal until the amplifier output settles. For this reason,
the current sources driving the feedback resistor are 20% higher
than those driving the input G_M resistor to provide an extra
margin.
Rail-to-rail Output Stage
The output stage is of rail-to-rail design, and has separate
supplies from the rest of the IC. The input GM stage and
feedback amplifiers are driven from the V_CC and V_EE supply pins
and only the output stage is powered by the V_CO and V_EO pins. A
typical supply arrangement when driving a 5V ADC is to have V_CO
connected to the ADC +5V supply and V_EO to ground. Therefore,
the ADC can never be overdriven beyond its supply rails. In this
configuration, the common-mode input range of the feedback
amplifier limits the dynamic range of the output stage. The input
and feedback amplifiers are not rail-to-rail, so the V_CC must be
more positive than V_CO and V_EE more negative than V_EO by the
feedback amplifier saturation voltage (±3V).
DC Offsets and Noise
There are three offset and noise sources in the ISL70617SEH:
the input, feedback, and I_ERR. The input has a low input noise
voltage and offset, which dominates at gains ~30 and above. The
feedback G_M stage has similar errors, but is never dominant
compared to I_ERR and is generally ignored. I_ERR can be thought of
as the mistracking and noise of the internal 100µA current
sources. Use Equation 19 and quantify these errors at the output
(RTO).
V_OS(RTO) = V_OS(IN)*Gain + I_ERR*R_FB+V_OS(FB)
(EQ. 19)
Similarly, Equation 20 for noise:
V_N(RTO₎₂ = (V_N(IN)*Gain)² + (I_n(err)*R_FB)²
(EQ. 20)
Reducing R_FB to the minimum value required for linear output
swing will improve output offsets and noise directly.
Another result of scaling R_FB is that the -3dB bandwidth is also
inversely scaled. Highest bandwidth will then be available at
lowest R_f. The ISL70617SEH is designed to be stable with
R_FB = 30.1kΩ minimum.
Having set R_FB to establish the output range, R_IN is set to
establish Gain = R_FB/R_IN. While -3dB bandwidth does diminish
for R_IN < 500Ω, this still allows fairly constant bandwidth over a
wide variety of gains. Similar to the resistor-oriented op amp
topology, parasitic capacitance at the R_FB node will peak the
frequency response. The ISL70617SEH is designed to be tolerant
to parasitic capacitances at R_FB from values of 2pF to 20pF. The
input stage is more tolerant, allowing 2pF to 30pF. Electronic
analog switches can be used to alter R_IN selections for gain
switching, as long as the minimum R_FB halves are connected to
the R_IN pins directly, with the switch(es) in between the halves.
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FN8697.4
December 16, 2016