MAX1533 Datasheet, PDF (28/38 Pages) Maxim Integrated Products – High-Efficiency, 5x Output, Main Power-Supply Controllers for Notebook Computers

High-Efficiency, 5x Output, Main Power-Supply
Controllers for Notebook Computers
• Maximum Load Current. There are two values to
consider. The peak load current (I_LOAD(MAX)) deter-
mines the instantaneous component stresses and fil-
tering requirements and thus drives output-capacitor
selection, inductor saturation rating, and the design
of the current-limit circuit. The continuous load cur-
rent (I_LOAD) determines the thermal stresses and
thus drives the selection of input capacitors,
MOSFETs, and other critical heat-contributing com-
ponents.
• Switching Frequency. This choice determines the
basic trade-off between size and efficiency. The
optimal frequency is largely a function of maximum
input voltage, due to MOSFET switching losses that
are proportional to frequency and V_IN². The opti-
mum frequency is also a moving target, due to rapid
improvements in MOSFET technology that are mak-
ing higher frequencies more practical.
• Inductor Operating Point. This choice provides
trade-offs between size vs. efficiency and transient
response vs. output ripple. Low inductor values pro-
vide better transient response and smaller physical
size, but also result in lower efficiency and higher
output ripple due to increased ripple currents. The
minimum practical inductor value is one that causes
the circuit to operate at the edge of critical conduc-
tion (where the inductor current just touches zero
with every cycle at maximum load). Inductor values
lower than this grant no further size-reduction bene-
fit. The optimum operating point is usually found
between 20% and 50% ripple current. When pulse
skipping (SKIP low and light loads), the inductor
value also determines the load-current value at
which PFM/PWM switchover occurs.
Inductor Selection
The switching frequency and inductor operating point
determine the inductor value as follows:
( ) _{L =}
V_OUT V_IN - V_OUT
V_IN f_OSC I_LOAD(MAX) LIR
For example: I_LOAD(MAX) = 5A, V_IN = 12V, V_OUT = 5V,
f_OSC = 300kHz, 30% ripple current or LIR = 0.3.
5V × ₍12V - 5V₎
L=
= 6.50µH
12V × 300kHz × 5A × 0.3
Find a low-loss inductor with the lowest possible DC
resistance that fits in the allotted dimensions. Most
inductor manufacturers provide inductors in standard
values, such as 1.0µH, 1.5µH, 2.2µH, 3.3µH, etc. Also
look for nonstandard values, which can provide a better
compromise in LIR across the input voltage range. If
using a swinging inductor (where the no-load induc-
tance decreases linearly with increasing current), evalu-
ate the LIR with properly scaled inductance values. For
the selected inductance value, the actual peak-to-peak
inductor ripple current (∆I_INDUCTOR) is defined by:
( ) _{∆IINDUCTOR}
=
V_OUT V_IN - V_OUT
V_IN f_OSC L
Ferrite cores are often the best choice, although pow-
dered iron is inexpensive and can work well at 200kHz.
The core must be large enough not to saturate at the
peak inductor current (I_PEAK):
I_PEAK
=
I_LOAD(MAX)
+
∆I_INDUCTOR
2
Transformer Design (For the MAX1537
Auxiliary Output)
A coupled inductor or transformer can be substituted
for the inductor in the 5V SMPS to create an auxiliary
output (Figure 1). The MAX1537 is particularly well suit-
ed for such applications because the secondary feed-
back threshold automatically triggers DL5 even if the
5V output is lightly loaded.
The power requirements of the auxiliary supply must be
considered in the design of the main output. The trans-
former must be designed to deliver the required current
in both the primary and the secondary outputs with the
proper turns ratio and inductance. The power ratings of
the synchronous-rectifier MOSFETs and the current
limit in the MAX1537 must also be adjusted according-
ly. Extremes of low input-output differentials, widely dif-
ferent output loading levels, and high turns ratios can
further complicate the design due to parasitic trans-
former parameters such as interwinding capacitance,
secondary resistance, and leakage inductance. Power
from the main and secondary outputs is combined to
get an equivalent current referred to the main output.
Use this total current to determine the current limit (see
the Setting the Current Limit section):
I_TOTAL = P_TOTAL / V_OUT5
where I_TOTAL is the equivalent output current referred
to the main output, and P_TOTAL is the sum of the output
power from both the main output and the secondary
output:
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