ISL6753 Datasheet, PDF (11/15 Pages) Intersil Corporation – ZVS Full-Bridge PWM Controller

ISL6753
The inductor current, when reflected through the isolation
transformer and the current sense transformer to obtain the
current feedback signal at the sense resistor yields
V_CS
=
-^NN----^SP-----^⋅â‹---^RN-----^CC----^ST--



I_O
+
D_------⋅_---T_{----S----W---}
2L_O



V_I
N
⋅
N_-----S--
N_P
–

V_{O}



V
(EQ. 16)
where V_CS is the voltage across the current sense resistor
and I_O is the output current at current limit.
Since the peak current limit threshold is 1.00V, the total
current feedback signal plus the external ramp voltage must
sum to this value.
V_e + V_CS = 1
(EQ. 17)
Substituting EQs. 15 and 16 into EQ. 17 and solving for R_CS
yields
R_CS
=
N_-----P-----⋅_---N_{-----C----T- ⋅ --------------------------1----------------------------}
N_S
I_O
+
V_-----O--
L_O
T_SW


1_-π-
+
D_{-2--}
Ω
(EQ. 18)
For simplicity, idealized components have been used for this
discussion, but the effect of magnetizing inductance must be
considered when determining the amount of external ramp
to add. Magnetizing inductance provides a degree of slope
compensation to the current feedback signal and reduces
the amount of external ramp required. The magnetizing
inductance adds primary current in excess of what is
reflected from the inductor current in the secondary.
∆I_P
=
-^V----^I--^N-----^â‹---^D-----^T----^S----^W---
L_m
A
(EQ. 19)
where V_IN is the input voltage that corresponds to the duty
cycle D and Lm is the primary magnetizing inductance. The
effect of the magnetizing current at the current sense
resistor, R_CS, is
∆V_CS
=
∆_-----I_--P-----⋅_---R_----C----S--
N_CT
V
(EQ. 20)
If ∆V_CS is greater than or equal to Ve, then no additional
slope compensation is needed and R_CS becomes
R_CS
=
--------------------------------------------------------------^N----^C----^T---------------------------------------------------------------
N_-----S--
N_P
⋅

 ^{I O}
+
D_-----T_{----S----W---}
2L_O
⋅



V_I
N
⋅
N_-----S--
N_P
–

V_{O}


+
V_{-----I--N-----}⋅_---D_-----T_{----S---W----}
L_m
(EQ. 21)
If ∆V_CS is less than Ve, then EQ. 18 is still valid for the value
of R_CS, but the amount of slope compensation added by the
external ramp must be reduced by ∆V_CS.
Adding slope compensation is accomplished in the ISL6753
using the CTBUF signal. CTBUF is an amplified
representation of the sawtooth signal that appears on the CT
pin. It is offset from ground by 0.4V and is 2x the peak-to-
peak amplitude of CT (0.4 - 4.4V). A typical application sums
this signal with the current sense feedback and applies the
result to the CS pin as shown in Figure 7.
R9
R6
R_CS
1
2 CTBUF
3
4
ISL6753
5
6
7
8 CS
C4
FIGURE 7. ADDING SLOPE COMPENSATION
Assuming the designer has selected values for the RC filter
placed on the CS pin, the value of R9 required to add the
appropriate external ramp can be found by superposition.
V_e – ∆V_CS
=
(_---D_-----(_--V_{----C-----T---B----U----F-----–-----}0_---._--4_---)_----+-----0_---._--4_---)_----⋅_---R_-----6_-
R6 + R9
V
(EQ. 22)
Rearranging to solve for R9 yields
R9 = ⁽---^D-----⁽--^V----^C-----^T---^B----^U----^F-----–-----⁰---^.--⁴---⁾----–----^V-----^e----+-----^∆----^V----^C----^S-----+-----⁰----^.-⁴----⁾----^â‹---^R----⁶--
V_e – ∆V_CS
Ω
(EQ. 23)
The value of R_CS determined in EQ. 18 must be rescaled so
that the current sense signal presented at the CS pin is that
predicted by EQ. 16. The divider created by R6 and R9
makes this necessary.
R′_CS
=
R_-----6_-----+-----R_-----9_--
R9
⋅
R_CS
(EQ. 24)
Example:
V_IN = 280V
V_O = 12V
L_O = 2.0µH
Np/Ns = 20
Lm = 2mH
I_O = 55A
Oscillator Frequency, Fsw = 400kHz
Duty Cycle, D = 85.7%
N_CT = 50
11
FN9182.1
March 10, 2005