MAX15041_10 Datasheet, PDF (12/18 Pages) Maxim Integrated Products – Low-Cost, 3A, 4.5V to 28V Input, 350kHz, PWM Step-Down DC-DC Regulator with Internal Switches

Low-Cost, 3A, 4.5V to 28V Input, 350kHz, PWM
Step-Down DC-DC Regulator with Internal Switches
Inductor Selection
A larger inductor value results in reduced inductor ripple
current, leading to a reduced output ripple voltage.
However, a larger inductor value results in either a larger
physical size or a higher series resistance (DCR) and a
lower saturation current rating. Typically, inductor value
is chosen to have current ripple equal to 30% of load
current. Choose the inductor with the following formula:
L
=
V_OUT
f_SW × ∆I_L
× ^{⎛⎝⎜}1−
V_OUT
V_IN
⎞
⎠⎟
where f_SW is the internally fixed 350kHz switching fre-
quency, and ∆I_L is the estimated inductor ripple current
(typically set to 0.3 x I_LOAD). In addition, the peak
inductor current, I_{L_PK,} must always be below both the
minimum high-side MOSFET current-limit value,
I_{HSCL_MIN} (5A, typ), and the inductor saturation current
rating, I_{L_SAT}. Ensure that the following relationship is
satisfied:
I_{L _ PK}
=
I_LOAD
+
1
2
×
∆I_L
<
min(I_{HSCL _ MIN},I_{L _ SAT} )
Diode Selection
The MAX15041 requires an external bootstrap steering
diode. Connect the diode between V_DD and BST. The
diode should have a reverse voltage rating, higher than
the converter input voltage and a 200mA minimum cur-
rent rating. Typically, a fast switching or Schottky diode
is used in this application, but a simple low-cost diode
(1N4007) suffices.
Input Capacitor Selection
For a step-down converter, input capacitor C_IN helps to
keep the DC input voltage steady, in spite of discontin-
uous input AC current. Low-ESR capacitors are pre-
ferred to minimize the voltage ripple due to ESR.
Size C_IN using the following formula:
C_IN
=
f_SW
×
I_LOAD
∆V_{IN _ RIPPLE}
×
V_OUT
V_IN
Output-Capacitor Selection
Low-ESR capacitors are recommended to minimize the
voltage ripple due to ESR. Total output-voltage peak-to-
peak ripple is estimated by the following formula:
∆V_OUT
=
V_OUT
f_SW × L
× ^{⎛⎝⎜}1−
V_OUT
V_IN
⎞
⎠⎟
×
⎛
⎝⎜^{RESR _ COUT}
+
8×
1
f_SW ×
C_OUT
⎞
⎠⎟
For ceramic capacitors, ESR contribution is negligible:
R_{ESR _ COUT}
<<
8×
1
f_SW ×
C_OUT
For tantalum or electrolytic capacitors, ESR contribution
is dominant:
R_{ESR _ COUT}
>>
8×
1
f_SW ×
C_OUT
Compensation Design Guidelines
The MAX15041 uses a fixed-frequency, peak-current-
mode control scheme to provide easy compensation
and fast transient response. The inductor peak current is
monitored on a cycle-by-cycle basis and compared to
the COMP voltage (output of the voltage error amplifier).
The regulator’s duty-cycle is modulated based on the
inductor’s peak current value. This cycle-by-cycle con-
trol of the inductor current emulates a controlled current
source. As a result, the inductor’s pole frequency is
shifted beyond the gain-bandwidth of the regulator.
System stability is provided with the addition of a sim-
ple series capacitor-resistor from COMP to SGND. This
pole-zero combination serves to tailor the desired
response of the closed-loop system.
The basic regulator loop consists of a power modulator
(comprising the regulator’s pulse-width modulator,
compensation ramp, control circuitry, MOSFETs, and
inductor), the capacitive output filter and load, an out-
put feedback divider, and a voltage-loop error amplifier
with its associated compensation circuitry. See Figure 1
for a graphical representation.
The average current through the inductor is expressed as:
I_L = G_MOD × V_COMP
where I_L is the average inductor current and G_MOD is
the power modulator’s transconductance. For a buck
converter:
V_OUT = R_LOAD × I_L
where R_LOAD is the equivalent load resistor value.
Combining the two previous equations, the power mod-
ulator’s transfer function in terms of V_OUT with respect
to V_COMP is:
V_OUT
V_COMP
=
R_LOAD
⎛ I_L
× I_L
⎞
= R_LOAD
× G_MOD
⎝⎜ G_MOD ⎠⎟
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