MC34262_11 Datasheet, PDF (7/19 Pages) ON Semiconductor – Power Factor Controllers

MC34262, MC33262
Operating Description
The MC34262, MC33262 contain many of the building
blocks and protection features that are employed in modern
high performance current mode power supply controllers.
There are, however, two areas where there is a major
difference when compared to popular devices such as the
UC3842 series. Referring to the block diagrams in
Figures 20, 21, and 22 note that a multiplier has been added
to the current sense loop and that this device does not
contain an oscillator. The reasons for these differences will
become apparent in the following discussion. A description
of each of the functional blocks is given below.
Rectifiers
PFC Preconverter
Converter
AC
Line
High
+ Frequency
Bypass
Capacitor
MC34362
+
Bulk
Storage
Capacitor
Load
Figure 18. Active Power Factor Correction Preconverter
Error Amplifier
An Error Amplifier with access to the inverting input and
output is provided. The amplifier is a transconductance
type, meaning that it has high output impedance with
controlled voltage−to−current gain. The amplifier features
a typical gm of 100 mmhos (Figure 6). The noninverting
input is internally biased at 2.5 V ± 2.0% and is not pinned
out. The output voltage of the power factor converter is
typically divided down and monitored by the inverting
input. The maximum input bias current is − 0.5 mA, which
can cause an output voltage error that is equal to the product
of the input bias current and the value of the upper divider
resistor R₂. The Error Amp output is internally connected
to the Multiplier and is pinned out (Pin 2) for external loop
compensation. Typically, the bandwidth is set below 20 Hz,
so that the amplifier’s output voltage is relatively constant
over a given ac line cycle. In effect, the error amp monitors
the average output voltage of the converter over several
line cycles. The Error Amp output stage was designed to
have a relatively constant transconductance over
temperature. This allows the designer to define the
compensated bandwidth over the intended operating
temperature range. The output stage can sink and source
10 mA of current and is capable of swinging from 1.7 V to
6.4 V, assuring that the Multiplier can be driven over its
entire dynamic range.
A key feature to using a transconductance type amplifier,
is that the input is allowed to move independently with
respect to the output, since the compensation capacitor is
connected to ground. This allows dual usage of of the
Voltage Feedback Input pin by the Error Amplifier and by
the Overvoltage Comparator.
Overvoltage Comparator
An Overvoltage Comparator is incorporated to eliminate
the possibility of runaway output voltage. This condition
can occur during initial startup, sudden load removal, or
during output arcing and is the result of the low bandwidth
that must be used in the Error Amplifier control loop. The
Overvoltage Comparator monitors the peak output voltage
of the converter, and when exceeded, immediately
terminates MOSFET switching. The comparator threshold
is internally set to 1.08 V_ref. In order to prevent false
tripping during normal operation, the value of the output
filter capacitor C₃ must be large enough to keep the
peak−to−peak ripple less than 16% of the average dc
output. The Overvoltage Comparator input to Drive Output
turn−off propagation delay is typically 400 ns. A
comparison of startup overshoot without and with the
Overvoltage Comparator circuit is shown in Figure 24.
Multiplier
A single quadrant, two input multiplier is the critical
element that enables this device to control power factor.
The ac full wave rectified haversines are monitored at Pin 3
with respect to ground while the Error Amp output at Pin 2
is monitored with respect to the Voltage Feedback Input
threshold. The Multiplier is designed to have an extremely
linear transfer curve over a wide dynamic range, 0 V to
3.2 V for Pin 3, and 2.0 V to 3.75 V for Pin 2, Figures 2 and
3. The Multiplier output controls the Current Sense
Comparator threshold as the ac voltage traverses
sinusoidally from zero to peak line, Figure 18. This has the
effect of forcing the MOSFET on−time to track the input
line voltage, resulting in a fixed Drive Output on−time, thus
making the preconverter load appear to be resistive to the
ac line. An approximation of the Current Sense
Comparator threshold can be calculated from the following
equation. This equation is accurate only under the given
test condition stated in the electrical table.
V_CS, Pin 4 Threshold ≈ 0.65 (V_{Pin 2} − V_th(M)) V_{Pin 3}
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